AD9762 データシートの表示（PDF） - Analog Devices

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AD9762

12-Bit, 125 MSPS TxDAC® D/A Converter

Analog Devices 

AVDD

1.2V

AD1580

AVDD

OPTIONAL

BANDLIMITING

CAPACITOR

REFLO

COMP1 AVDD

RFB

VDD

OUT1

OUT2

AD7524 VREF

AGND

DB7–DB0

0.1V TO 1.2V

RSET

IREF =

VREF/RSET

+1.2V REF

REFIO

FS ADJ

AD9762

50pF

CURRENT

SOURCE

ARRAY

Figure 43. Single-Supply Gain Control Circuit

AD9762

The second method may be used in a dual-supply system in

which the common-mode voltage of REFIO is fixed and IREF is

varied by an external voltage, VGC, applied to RSET via an ampli-

fier. An example of this method is shown in Figure 44 in which

the internal reference is used to set the common-mode voltage

of the control amplifier to 1.20 V. The external voltage, VGC, is

referenced to ACOM and should not exceed 1.2 V. The value

of RSET is such that IREFMAX and IREFMIN do not exceed 62.5 µA

and 625 µA, respectively. The associated equations in Figure 44

can be used to determine the value of RSET.

OPTIONAL

BANDLIMITING

CAPACITOR

AVDD

REFLO

COMP1 AVDD

+1.2V REF

50pF

REFIO

CURRENT

1␮F

FS ADJ

SOURCE

ARRAY

RSET IREF

AD9762

IREF = (1.2–VGC)/RSET

VGC

WITH VGC < VREFIO AND 62.5␮A Յ IREF Յ 625A

Figure 44. Dual-Supply Gain Control Circuit

In some applications, the user may elect to use an external con-

trol amplifier to enhance the multiplying bandwidth, distortion

performance, and/or settling time. External amplifiers capable

of driving a 50 pF load such as the AD817 are suitable for this

purpose. It is configured in such a way that it is in parallel with

the weaker internal reference amplifier as shown in Figure 45.

In this case, the external amplifier simply overdrives the weaker

reference control amplifier. Also, since the internal control

amplifier has a limited current output, it will sustain no damage

if overdriven.

EXTERNAL

CONTROL AMPLIFIER

VREF

INPUT

RSET

REFLO

+1.2V REF

REFIO

FS ADJ

AD9762

AVDD

COMP1 AVDD

50pF

CURRENT

SOURCE

ARRAY

Figure 45. Configuring an External Reference Control

Amplifier

ANALOG OUTPUTS

The AD9762 produces two complementary current outputs,

IOUTA and IOUTB, which may be configured for single-ended or

differential operation. IOUTA and IOUTB can be converted into

complementary single-ended voltage outputs, VOUTA and VOUTB,

via a load resistor, RLOAD, as described in the DAC Transfer

Function section by Equations 5 through 8. The differential

voltage, VDIFF, existing between VOUTA and VOUTB can also be

converted to a single-ended voltage via a transformer or differ-

ential amplifier configuration. The ac performance of the

AD9762 is optimum and specified using a differential trans-

former coupled output in which the voltage swing at IOUTA and

IOUTB is limited to ± 0.5 V. If a single-ended unipolar output is

desirable, IOUTA should be selected.

The distortion and noise performance of the AD9762 can be

enhanced when the AD9762 is configured for differential opera-

tion. The common-mode error sources of both IOUTA and IOUTB

can be significantly reduced by the common-mode rejection of a

transformer or differential amplifier. These common-mode

error sources include even-order distortion products and noise.

The enhancement in distortion performance becomes more

significant as the frequency content of the reconstructed wave-

form increases. This is due to the first order cancellation of

various dynamic common-mode distortion mechanisms, digital

feedthrough and noise.

Performing a differential-to-single-ended conversion via a

transformer also provides the ability to deliver twice the recon-

structed signal power to the load (i.e., assuming no source

termination). Since the output currents of IOUTA and IOUTB are

complementary, they become additive when processed differen-

tially. A properly selected transformer will allow the AD9762 to

provide the required power and voltage levels to different loads.

Refer to Applying the AD9762 section for examples of various

output configurations.

The output impedance of IOUTA and IOUTB is determined by the

equivalent parallel combination of the PMOS switches associ-

ated with the current sources and is typically 100 kΩ in parallel

with 5 pF. It is also slightly dependent on the output voltage

(i.e., VOUTA and VOUTB) due to the nature of a PMOS device.

As a result, maintaining IOUTA and/or IOUTB at a virtual ground

via an I-V op amp configuration will result in the optimum dc

linearity. Note, the INL/DNL specifications for the AD9762

are measured with IOUTA maintained at a virtual ground via an

op amp.

REV. B

–13–

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